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Implementation of some transmission line systems requires coaxial transmission lines sections of length to deliver some specific characteristics. Examples are series transformation sections such as quarter wave series sections, wave traps such as shunt quarter wave o/c stubs etc.
The physical length of a line section is not the same as its electrical length, and they are related by the Velocity Factor (VF) where VF=PhysicalLength/ElectricalLength.
(Silver 2011) gives a definition above of Velocity Factor in terms of the dielectric constant. Readers could be forgiven for thinking that since most dielectrics used in practical transmission lines are fairly independent of frequency that VF is independent of frequency.
The formula give by Silver is a simplification for distortionless lines, and a lossless line is a special case of a distortionless line, but it is not true for lossy lines in general.
Most cable datasheets give a single figure for VF independent of frequency, further reinforcing the idea that it is independent of freqeuncy.
A common model for the behaviour of the distributed resistance, inductance, conductance, and capacitance is described by the Telegrapher's Equation.
For most practical coaxial cables at frequencies where skin effect is well developed, R is proportional to f^0.5, G is proportional to f, and L and C are independent of frequency. Measurement data and published cable specifications are a good fit to this model over the frequency range where the skin effect condition is satisfied.
Fig 1 shows the Matched Line Loss (MLL) of Belden 8216 (RG174) from their specifications, and a fit to the model MLL=k1f^0.5+k2f. The lower data points at 1 and 10MHz are clearly well above the model predictions, in fact at 1MHz the MLL is 250% of the model prediction. This cable was chosen because it is quite lossy and it uses stranded copper plated steel for the inner conductor, and the departure from the model is almost certainly due to inadequate copper thickness to satisfy the skin depth condition. (The strands are 80µm radius and would need at least 195 radial copper thickness to give copper like performance at 1MHz... physically impossible.)
At lower frequencies, whilst G and C are probably unchanged, both R and L are higher than predicted by the higher frequency cable data (loss dataset and nominal Zo and VF).
(Maguire 2011) in his program TLDetails and explanatory workbook TLine Model.xls calculates RLGC in the transition region using Rdc in addition to the loss model mentioned above. The method attributed to H Johnson does not seem to take account for instance nonhomogenous conductors, particularly with magnetic materials and stranding of same.
Table 1 compares Belden's datasheet MLL with those of TLDetails and TLLC. TLLC uses a regression based on Belden's data with the exclusion of the datapoints at 1 and 10MHz because they are significant departures from the model. The consequence is that TLLC predictions below 50MHz would be extrapolations and less accurate so they are not shown. (TLLC shows the frequency range on which its model is based, and that frequency range is shown in red when the user has requested a frequency outside that range, users are cautioned against extrapolated results.)
TLDetails error is 49% over 1100MHz, which questions Johnson's and Macquire's method, at least for this cable type.
A closed form solution that properly deals with the range of centre conductor constructions and materials and shield constructions and materials used in practical cables would be very challenging.
Without some assured method for predicting the change in R and L, a method that works in this case of stranded plated steel centre conductor, and in the more general case for the range of centre conductor constructions and materials and shield constructions and materials, one must resort to measurement.
Measurement of VF is often taken as trivial, and the common technique is to find the lowest frequency at which the input impedance of a o/c stub is zero, and VF=PhysicalLength/(c0/f/4)=PhysicalLength/(299792458/f/4). For example, if X=0 at 49.47MHz for a 1m o/c stub, VF=0.660.
That seems simple enough, but is it correct?
This method assumes that the input reactance of a 90° long o/c stub is zero, and whilst that is true for distortionless lines (including a lossless line) it is not true in general and the error may be significant.
If we assume for a moment that L is unchanged, we can calculate the effect of R on a 90° o/c stub at 1MHz. Fig 2 shows that the reactance at 1MHz (90° electrical length) is not zero but almost 4Ω. A small increase in L due to the extra flux resulting from the current reaching further into the interior of the centre conductor would result in X somewhat lower (ie more negative).
(Brown 2011) explains a classic method of measuring VF.
Q: Can I measure a long spool of coax as a stub to find its length?
A: Yes, but there's a bit more to the measurement than meets the eye. That's because the velocity factor Vf is not a constant – it varies with frequency. The variation is small in the HF spectrum, but, for many cables, can be quite significant at low radio frequencies. Vf starts out very low at audio frequencies, but quickly begins rising at low radio frequencies until it settles at the familiar published value. The graph at the right is measured data for Commscope 3227, a high quality RG8 coaxial cable. The published Vf for this cable is 0.84. Measurements were made by connecting a full 1,000 ft spool of cable as a stub in a precision 50 ohm system and observing the frequency of the nulls. The quarter wave resonance was 194.5 kHz. Additional nulls were measured up to 3.8 MHz (19 quarter waves). ...
Fig 3 is Brown's plot of his measurement results certainly support the proposition that VF varies with frequency, particularly in the transition region. If his measurements depended on X=0 at all odd 90° length multiples, the small ve X Zin component at 90° length multiples in the transition region would mean the frequency recorded would have been a little above that for the 90° length multiple, and so overestimate the reduction in VF, ie the reduction in VF at lower frequencies would well be somewhat less than plotted.
Another method is to measure Zin for a line section with s/c and o/c termination over a range of frequencies and calculate the line parameters from Zoc(f) and Zsc(f).
Measuring a nominal quarter wave section may not be trivial!
The first step is to determine what the application requires at the frequency of interest, for example:
Though a line section may be 90° electrical length, 90° phase delay of V_{out}/V_{in} and I_{out}/I_{in} occurs when the line is terminated in its (actual) characteristic impedance, which may be different to its nominal characteristic impedance. Few applications terminate the line section in its actual characteristic impedance. For example, using published specifications of Belden 8262 (RG58C/U), an electrical quarter wave at 1MHz terminated in a load of 50+j0Ω has V_{out}/V_{in} equal to 9.252e1∠87.5°, a phase error of 2.5°.
Further, as shown in Fig 3, the input reactance of an o/c stub many not be zero at 90° electrical length, and as a consequence input impedance may not be a minimum at 90° electrical length.
Some key characteristics that help find a practical solution to problems:
If the phase delay of output voltage or current over input voltage or current in a quarter wave line section is critical, measure the phase delay at the desired frequency with the applicable load and adjust physical length to obtain the required phase shift.
At higher frequencies using low loss line, an o/c 90° electrical length stub will have input reactance very close to zero, and impedance very close to minimum, sufficiently close that error in the method will be masked by practical measurement error.
Version  Date  Description 
1.01  16/09/2012  Initial. 
1.02  
1.03 
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