The ‘net abounds with calculators for design of small transmitting loops (STL), and most estimate the voltage impressed on the tuning capacitor. Most of these calculators give an incorrect estimate.
This article describes a measurement based approach to estimating the capacitor voltage for a STL.
Continue reading Estimating the voltage impressed on the tuning capacitor of a small transmitting loop
The ‘net abounds with articles describing easy to build low cost small transmitting loops (STL).
This article describes measurement of a STL for 4MHz using RG213 coaxial cable for the main loop and its tuning capacitance, and a smaller plain wire loop for transformation to 50Ω. Continue reading A QRP small transmitting loop evaluation
Precise RF have announced two small transmitting loops for amateur radio, this article looks at the Precise High Gain Loop.
The antenna is described at (Precise RF 2017).
Above is an extract from a table in the brochure comparing the subject antenna to some others.
On a quick scan, the standout figure is gain of 2.8dBd presumably at a loop height of 4.57m (15′), and without qualification of frequency. Elsewhere in the brochure there is a note that 80m requires an optional ‘resonator’… presumably a larger loop.
The ITU Radio Regulations (ITU 2012) gives us a definition for antenna gain that captures the meaning of dBd that is accepted by most regulators and industry world wide. Continue reading Precise RF small transmitting loop
As the popularity of low cost, low end antenna analysers increases, client software appears to enhance the capability of the analyser.
The SARC-100 is one of these low end analysers, it and its many close derivatives are marketed under various model names.
The sign of reactance discusses a major weakness of these and many other low end instruments in that they do not ‘measure’ the sign of reactance, displaying the magnitude of reactance and leaving it to the user to solve the sign problem.
SM6WHY is one of the many who have produced software for the SARC-100 that purports to solve the sign of reactance problem. He gives this graphic on his website to demonstrate the capability of his software used with a SARC-100 (which does not sense the sign of reactance).
Above is part of the graphic he offers. Though the image is poor quality, the VSWR plot appears smooth and quite typical of that which might be obtained by measuring an antenna system near its VSWR minimum.
However the accompanying Smith chart plot which has points plotted with both negative and positive reactance is inconsistent with the VSWR plot and appears flawed. Continue reading The sign of reactance – SM6WHY’s take
Shunt matching a loaded HF whip with just a VSWR meter gave a direct answer and supporting explanation to an online poster’s question about optimising an 80m loaded mobile vertical with shunt matching, specifically the inductor needed and an adjustment procedure.
The original poster clearly had the impression that this improvement of the original VSWR=1.3 would make a large difference.
The only other option for me is to remove the shunt and set my swr back to 1.3:1 and not be able to communicate.
Continue reading Shunt matching a loaded HF whip – discussion
A question was asked on one of the popular online forums:
How to get the most out of an 80 mobile antenna?…I am using a hustler antenna and I had the swr down to 1.3:1. I started researching how to make the antenna better and it seems that maybe an inductive shunt at the base of the antenna to ground would help. I don’t have the equipment to analyze the antenna and the shunt reactance. I made a 9 turn coil 1″ in diameter and 1″ long using n0. 12 awg thnn wire. I installed the coil at the base of the antenna and now the best swr that I can get is 1.8:1. So is there a way that I can set up the coil and antenna using only an swr meter?…
After 50 responses, none of the online experts have offered a direct answer or explanation.
The coil inductance is too low, try a solenoid of 13 turns, 40mm diameter and 40mm length.
An antenna of this type at minimum VSWR will have a feed point impedance of near zero reactance and resistance equal to 50 divided by the measured VSWR, so in this case 39Ω. Continue reading Shunt matching a loaded HF whip with just a VSWR meter
A correspondent wrote suggesting that he had seen online NEC patterns showing a 30″ square small untuned loop to have a gain of around 10dBi, more than 30dB better than given by Calculate small loop Antenna Factor.
Firstly, lets describe a loop for study, a square diamond with sides of 760mm (30″) of 2mm diameter copper fed in one corner at 7.1MHz.
Calculate small loop Antenna Factor models a small loop in free space (therefore does not include ground losses).
Above is the calculator result, the key figures are Antenna Factor 31.75dB and Gain -44.5dBi.
An NEC-4.2 model was constructed with external excitation (1V/m) incident on the loop which has a 50+j0Ω load inserted at the feed point to represent the receiver load.
Here is the model source.
CM Small square untuned loop CM NEC-4.2 CM CM 1. Plane wave excitation CM CM Owen Duffy CM Note: rotations might not work properly in various NEC-2 versions, beware of segment size issues in NEC-2. CE GW 1 5 -0.38 0 -0.38 0.38 0 -0.38 0.001 GM 1 3 0 90 0 0 0 0 1 GM 0 0 0 90 0 0 0 2 1 GE 0 LD 5 0 0 0 58000000 LD 4 1 1 1 50 0 GN -1 EK EX 1 1 1 0 45 0 0 0 0 0 FR 0 0 0 0 7.1 0 EN
The key result to be extracted from the model run is the current in the 50Ω resistor in segment 1 of wire 1. The magnitude of the current is 5.1204E-04, so the voltage developed in the resistor V=5.1074-04*50=0.02554V. Antenna Factor is the ratio of the E field excitation to the terminal voltage of the receiver, so in dB it is 20*log(1/0.02554) =31.83 dB/m.
The NEC model’s 31.83 dB/m is close to the calculator prediction of 31.75dB/m, but includes the benefit of the lossy ground reflection . Continue reading Small untuned loop for receiving – NEC model
Frank, W3LPL conducted two interesting experiments with WSPRlites on 20m from the US to Europe essentially. This article discusses the first test.
The first experiment was a calibration run if you like to explore the nature of simultaneous WSRP SNR reports for two transmitters using different call signs on slightly different frequencies (19Hz in this case) feeding approximately the same power to the same antenna.
The first test uses two WSPRlites feeding the same antenna through a magic-T combiner producing a data set consisting of 900 pairs of SNR reports from Europe with only about 70 milliwatts from each WSPRlite at the antenna feed.
The data for the test interval was extracted from DXplorer, and the statistic of main interest is the paired SNR differences, these are the differences in a report from the same station of the two signals in the same measurement WSPR interval.
There is an immediate temptation of compare the average difference, it is simple and quick. But, it is my experience that WSPR SNR data are not normally distributed and applying parametric statistics (ie statistical methods that depend on knowledge of the underlying distribution) is seriously flawed.
We might expect that whilst the observed SNR varies up and down with fading etc, that the SNR measured due to one transmitter is approximately equal to that of the other, ie that the simultaneous difference observations should be close to zero in this scenario.
What of the distribution of the difference data?
Above is a frequency histogram of the distribution about the mean (0). Interpretation is frustrated by the discrete nature of the SNR statistic (1dB steps), it is asymmetric and a Shapiro-Wik test for normality gives a probability that it is normal p=1.4e-43.
So lets forget about parametric statistics based on normal distribution, means, standard deviation, Student’s t-test etc are unsound for making inferences because they depend on normality.
Nevertheless, we might expect that there is a relationship between the SNR reports for both transmitters, We might expect that SNR_W3GRF=SNR_W3LPL.
So, lets look at the data in a way that might expose such a relationship.
Above is a 3D plot of the observations which shows the count of spots for each combination of SNR due to the two transmitters. The chart shows us that whilst there were more spots at low SNR, the SNRs from both are almost always almost the same.
A small departure can be seen where a little ridge exists in front of the main data.
Lets look at in 2D. Continue reading W3LPL’s paired WSPRlite test – test 1
A correspondent reading recent articles on active loops for receiving asks:
I have a 30″ square loop of #12 wire that I use for receiving, and when I attach it to the receiver on 40m, the audio output voltage goes up three times or more. Do I need an amplifiers, or will it worsen things?
It is possible to determine the ambient noise temperature from the true noise power change over that of a matched termination.
The equivalent noise temperature of the receiver is implied by its Noise Figure when it is terminated with a matched termination. Noise due to an open circuit or short circuit input is not defined.
The correspondent re-measured with a termination, and as it turned out, the results were much the same, so lets work the case of voltage increasing by a factor of three.
Without going any further, we can calculate the degradation in External S/N by the receiver, total noise power is proportional to (3^2) times internal noise, so S/N degradation is 10*log(9/(9-1))=0.51dB… very little.
It is true that an amplifier is unlikely to improve things and will be likely to degrade things because of intermodulation distortion that is inherent in them, more so if it overloads on broadband signal input.
But let’s go on to estimate the ambient noise figure Fa.
It is really important for this process that the AGC does not change the receiver gain, and there is no overload or clipping. The latter means DO NOT SWITCH THE AGC OFF, the S meter deflects, you need extra input attenuation to keep things linear.
Now lets assume the receiver has a Noise Figure of 6dB (most modern HF transceivers are in that ball park).
We need to estimate the gain of the antenna, we will use Calculate small loop Antenna Factor.
Ok, terminated in 50Ω, the untuned small loop has a gain of -43.4dBi. So, it captures only a very small portion of the external noise, but even so it delivers sufficient to the receiver to increase the output voltage by a factor of 3. Continue reading Small untuned loop for receiving – is an amplifier necessary?
Small untuned loop for receiving set out a model for calculating the S/N degradation of an active untuned small loop antenna system.
The calculations in Small untuned loop for receiving – Trask noise and gain analysis might prompt the question of what is the optimal resistive load for an untuned small loop.
This article explores the topic for a simple model where the equivalent noise temperature of the amplifier is independent of source impedance.
We can construct a simple model where the loop behaves as a fixed pure inductance, and its load is a fixed pure resistance.
This is a reasonably good model for a small loop, perimeter < wl/10, not too bad for perimeter up to wl/3.
The source impedance becomes the loop’s inductive reactance Xl which is proportional to frequency, and the load is Rl.
Above is a plot of the relative power developed in the load vs the ratio of Rl/Xl.
There is a maximum where Rl=Xl, and the power captured falls away either side. Continue reading Small untuned loop for receiving – optimal loop load resistance